Inverter suitable for use with portable AC power supply unit

ABSTRACT

An inverter includes a DC power supply circuit, an inverter circuit having a plurality of switching elements and switching an output of the DC power supply circuit on the basis of a PWM signal to deliver a high-frequency voltage, a filter circuit converting the high-frequency voltage to a substantially sinusoidal AC voltage, a power detector detecting an effective or wattless power of the AC power, a phase angle calculator calculating a phase angle of current relative to voltage from the detected effective or wattless power, a phase detector detecting a leading or lagging state of the phase angle, and a controller decreasing a frequency of the output voltage when the phase detector detects the leading state of the phase angle, the controller increasing the frequency of the output voltage when the phase detector detects the lagging state of the phase angle.

BACKGROUND OF THE INVENTION

[0001] 1. Field of the invention

[0002] This invention relates to an inverter suitable for use withportable AC power supply units.

[0003] 2. Description of the related art

[0004] Inverters have been incorporated in portable AC power supplyunits, drivers of AC motors, uninterruptable power supply units, etc. Asone of modes of application, a plurality of, for example, two portableAC power supply units are connected in parallel with each other to drivea load. In this case, the portable AC power supply units are operatedwith output frequencies in synchronism with each other. Current (crosscurrent) flows from one of the power supply units to the other when achange in the load etc. results in a subtle change in the frequency ofeither power supply unit. The cross current sometimes breaks circuitcomponents of the portable AC power supply unit. The cross current flowsfrom the power supply unit with a higher output frequency to the onewith a lower output frequency.

[0005] As one of measures preventing the cross current flowing betweenthe portable AC power supply units, a lag or lead in a phase betweenoutput voltage and output current is monitored. An output frequency isadjusted on the basis of the phase lag or lead, whereby the crosscurrent is prevented. FIG. 22 shows one of the conventional arrangementsfor preventing the cross current. A portable AC power supply unit 1comprises an engine drive AC generator 2 and an inverter unit 3 havingoutput terminals 3 a and 3 b from which a sinusoidal AC voltage isdelivered. The inverter unit 3 includes a rectifier circuit 4 rectifyinga three-phase AC voltage generated by the AC generator 2, a smoothingcapacitor 5, a single-phase full-bridge inverter circuit 6, a filtercircuit 7, a control circuit 8 and a drive circuit 9. The controlcircuit 8 includes a microcomputer 10 and a pulse-width-modulation (PWM)circuit 11 generating a drive signal. The inverter circuit 6 is adaptedto be connected to a load. When a plurality of the portable AC powersupply units 1 are to be connected to each other, the inverter circuits6 of the respective power supply units 1 are connected to each other.

[0006] In the above-described arrangement, the control circuit 8controls the generator 2 so that the engine maintains a predeterminednumber of revolution. The control circuit 8 further performs a PWMcontrol so that a sine wave AC voltage having a predetermined voltage(for example, an effective value of 100V) at a predetermined frequency(50 Hz or 60 Hz) is delivered from the output terminals 3 a and 3 b. Thecontrol circuit 8 further includes an output voltage detecting circuit12 detecting an output voltage of the inverter circuit 6, an outputcurrent detecting circuit 13 detecting an output current of the invertercircuit 6 and a phase difference detecting circuit 14 detecting a phasedifference between the output voltage and the output current. Thecontrol circuit 8 increases an output frequency when the output currentlags behind the output voltage. Further, the control circuit 8 decreasesthe output frequency when the output current leads the output voltage.Consequently, an output balance is achieved between the two AC powersupply units 1 connected in parallel with each other. The outputfrequencies are adjusted in a range between 49.90 Hz and 50.10 Hz whenthe portable AC power supply units are of 50 Hz specification.

[0007] In the above-mentioned detection of the phase difference, thephase difference is detected by measuring a time from a zero cross pointof the output voltage (AC) to a zero cross point of the output current.However, when a detected waveform of the output current is distorted,the zero crossing may occur twice or the timing of the zero crossing maynot be normal. As a result, the output currents are not balanced betweenthe power supply units in a parallel operation of the power supplyunits.

SUMMARY OF THE INVENTION

[0008] Therefore, an object of the present invention is to provide aninverter in which the output currents are balanced in the paralleloperation of the power supply units.

[0009] The present invention provides an inverter comprising a DC powersupply circuit, an inverter circuit having a plurality of switchingelements and switching an output of the DC power supply circuit on thebasis of a PWM signal to deliver a high-frequency voltage, a filtercircuit converting the high-frequency voltage to a substantiallysinusoidal AC voltage, a power detector detecting an effective orwattless power of the AC power, a phase angle calculator calculating aphase angle of current relative to voltage from the detected effectiveor wattless power, a phase detector detecting a leading or lagging stateof the phase angle, and a controller decreasing a frequency of theoutput voltage when the phase detector detects the leading state of thephase angle, the controller increasing the frequency of the outputvoltage when the phase detector detects the lagging state of the phaseangle.

[0010] According to the above-described arrangement, the effective poweror wattless power contains a phase angle element between the outputvoltage and the output current. The effective or wattless power isdetected, and the phase angle calculator calculates a phase angle on thebasis of the detected effective or wattless power. Consequently, anaccurate phase angle can be detected even when the output current or theoutput current detector contains a waveform distortion and accordingly,the accuracy in the detection of the phase angle can be improved.Furthermore, the phase detector detects the leading or lagging state ofthe calculated phase angle, and the controller decreases the frequencyof the output voltage when the phase detector detects the leading stateof the phase angle. The phase detector increases the frequency of theoutput voltage when the phase detector detects the lagging state of thephase angle. Consequently, an accurate frequency control can be carriedout, and the output currents are balanced in the parallel operation ofthe power supply units.

BRIEF DESCRIPTION OF THE DRAWINGS

[0011] Other objects, features and advantages of the present inventionwill become clear upon reviewing the following description of apreferred embodiment, made with reference to the accompanying drawings,in which:

[0012]FIG. 1 is a circuit diagram showing an electrical arrangement of aportable AC power supply unit to which an inverter of an embodiment inaccordance with the present invention is applied;

[0013]FIG. 2 is a schematic block diagram showing functions of amicrocomputer employed in the power supply unit;

[0014]FIG. 3 is a graph showing a data table of sine wave referencedata;

[0015]FIG. 4 is a graph showing a sine wave reference signal and anoutput current detection signal;

[0016]FIG. 5 is a circuit diagram showing a part of a PWM circuit;

[0017]FIGS. 6A to 6C show waveforms at points in the circuit of FIG. 5respectively;

[0018]FIGS. 7A to 7C shows waveforms related to the PWM control;

[0019]FIG. 8 is a flowchart showing a control manner by themicrocomputer;

[0020]FIG. 9 shows frequency setting data;

[0021]FIG. 10 is a flowchart showing another control manner by themicrocomputer;

[0022]FIG. 11 shows a parallel operation of two portable AC power supplyunits with cross current due to output frequency occurring;

[0023]FIG. 12 shows a parallel operation of two portable AC power supplyunits with cross current due to output voltage occurring;

[0024]FIG. 13 is a flowchart showing a control manner in a secondembodiment in accordance with the invention;

[0025]FIG. 14 is a view similar to FIG. 9;

[0026]FIGS. 15A to 15C are waveform charts showing a third embodiment inaccordance with the invention;

[0027]FIGS. 16A to 16D are waveform charts showing a fourth embodimentin accordance with the invention;

[0028]FIG. 17 is a flowchart showing an overall control manner forcorrection in a fifth embodiment in accordance with the invention;

[0029]FIG. 18 is a flowchart showing a control manner for correction;

[0030]FIG. 19 is a flowchart showing a control manner for correctionusing sine wave reference data;

[0031]FIG. 20 is a waveform chart showing an output voltage signal andan output current signal;

[0032]FIG. 21 is a flowchart showing determination of a leading orlagging state of the output current; and

[0033]FIG. 22 is a view similar to FIG. 1, showing a conventional powersupply unit.

DETAILED DESCRIPTION OF PREFERRED EMBODIMENTS

[0034] An embodiment in accordance with the present invention will bedescribed with reference to FIGS. 1 to 12. The inverter of the inventionis incorporated in a portable AC power supply unit in the embodiment.Referring to FIG. 1, an electrical arrangement of the portable AC powersupply unit 21 generating AC power of 100 V and 50 Hz or 60 Hz, forexample. The portable AC power supply unit 21 comprises a three-phase ACgenerator 22 driven by an engine (not shown) and a single-phase inverterunit 23 connected to a rear stage of the generator. The generator 22includes a rotor, an armature neither of which is shown, and a steppingmotor 24 controlling a flow rate of fuel (gasoline) to the engine sothat a rotational speed of the engine is controlled. The armature hasY-connected primary windings 25 u, 25 v and 25 w wound thereon and anauxiliary winding 26 wound thereon. Primary winding terminals 27 u, 27 vand 27 w and auxiliary winding terminals 28 a and 28 b are connected toinput terminals 29 u, 29 v and 29 w, 30 a and 30 b of the inverter unit23 respectively.

[0035] The inverter unit 23 will be described in detail. A rectifiercircuit 33 is connected between DC power supply lines 31 and 32. Therectifier circuit 33 is further connected to the input terminals 29 u,29 v and 29 w. A smoothing capacitor 34 and an inverter circuit 37 arealso connected between the DC power supply lines 31 and 32. The invertercircuit 37 is further connected to output terminals 35 and 36 of theinverter unit 23. A filter circuit 38 is connected to the invertercircuit 37. The rectifier circuit 33 serves as a DC power supply circuitin the invention. The rectifier circuit 33 comprises thyristors 39 to 41and diodes 42 to 44 connected into a three-phase hybrid bridgeconfiguration. The inverter circuit 37 comprises transistors (switchingelements) 45 to 48 and diodes 49 to 52 connected into a full bridgeconfiguration.

[0036] The filter circuit 38 comprises a reactor 55 and a capacitor 56.The reactor 55 is interposed between the output terminal 53 of theinverter circuit 37 and the output terminal 35 of the inverter unit 23.The capacitor 56 is connected between the output terminals 35 and 36 ofthe inverter unit 23. The inverter circuit 37 has an output terminal 54directly connected to the output terminal 36 of the inverter unit 23. Acurrent transformer 57 is connected across a current path between theoutput terminal 54 and the filter circuit 38 for detecting an outputcurrent. In a parallel operation of a plurality of the AC power supplyunits 21, the output terminals 35 and 36 of the inverter units 23 areconnected in parallel with each other or one another, respectively.

[0037] The inverter unit 23 further comprises a control power supplycircuit 58, a control circuit 59 and a drive circuit 60. AC voltageinduced in the auxiliary winding 26 is supplied to input terminals 30 aand 30 b of the control power supply circuit 58. The supplied AC voltageis rectified and smoothed into a control DC voltage (5 V or ±15 V, forexample) for energizing the control circuit 59. The AC voltage inducedin the auxiliary winding 26 is also supplied to the control circuit 59for detection of the rotational speed of the engine. The control circuit59 comprises a microcomputer 61, a DC voltage detecting circuit 62, anoutput voltage detecting circuit 63, an output current detecting circuit64 and a pulse width modulation (PWM) circuit 65. The microcomputer 61comprises a CPU 61 a, a ROM 61 b and a RAM 61 c the latter two of whichserve as storage means, and a D/A converter 61 d serving as sine wavereference signal generator, as shown in FIG. 2. The microcomputer 61further includes an input/output port, an A/D converter, a timercircuit, an oscillator circuit none of which are shown. These componentsare incorporated into a one-chip IC.

[0038] The ROM 61 b stores as initial data sine wave reference data D(n)for one cycle where n changes from 1 to 256. FIG. 3 shows a data tableof the sine wave reference data. More specifically, an axis of abscissasdenotes a memory address sequence, whereas an axis of ordinates denotessine wave reference data D(n). The sine wave reference data D(n) issequentially increased or decreased between 1 and 256. The RAM 61 cstores new sine wave reference data D(n). The sine wave reference dataD(n) stored on the ROM 61 b includes 256 data for one cycle as shown inFIG. 3. The 256 data correspond to values of amplitude of a sine wavereference signal Vsin (as shown in FIG. 4). When the power supplyfrequency is at 50 Hz, the 256 data are sequentially read out by the CPU61 a at an equal time interval for {fraction (1/50)} sec. When the powersupply frequency is at 60 Hz, the 256 data are sequentially read out bythe CPU 61 a at an equal time interval for {fraction (1/60)} sec.

[0039] The DC voltage detecting circuit 62 detects DC voltage Vdcbetween the DC power supply lines 31 and 32 to deliver the detected DCvoltage as a DC voltage signal to the microcomputer 61. Themicrocomputer 61 inputs the DC voltage signal. The microcomputer 61turns off the thyristors 39 to 41 when the input DC voltage Vdc is above180 V. The microcomputer 61 turns on the thyristors 39 to 41 when theinput DC voltage Vdc is at or below 180 V. The output voltage detectingcircuit 63 serving as output current detector includes a voltage dividercircuit dividing voltage between the terminals 53 and 54 of the invertercircuit 37 and a filter eliminating carrier wave components from dividedrectangular wave voltage, neither of which is shown. The output voltagedetecting circuit 63 delivers an output voltage signal Vs to themicrocomputer 61 and the PWM circuit 65. The output current detectingcircuit 64 converts the output current detected by the currenttransformer 57 to a predetermined voltage level. The output currentdetecting circuit 64 delivers an output current signal Is as an outputcurrent signal to the microcomputer 61 and the PWM circuit 65. The PWMcircuit 65 executes a PWM control to generate drive signals Gi to G4 forthe transistors 45 to 48 respectively. The drive signals GI to G4 areapplied via the drive circuits 60 to the bases of the transistors 45 to48 respectively.

[0040] An output frequency of the microcomputer 61 is set at either 50Hz or 60 Hz by an input from an switch input section (not shown). Forexample, when an AC power supply of 50 Hz (100 V) is to be produced, thePWM circuit 65 is supplied with the sine wave reference signal Vsin asan AC reference voltage having a frequency equal to the set outputfrequency. The sine wave reference signal Vsin is supplied to an erroramplifier circuit 66 of the PWM circuit 65 as shown in FIG. 5. The erroramplifier circuit 66 is also supplied with an output voltage signal Vsdelivered by the output voltage detecting circuit 63. The erroramplifier circuit 63 executes amplification by subtraction to deliver aPWM control signal Vsin′, whereupon the output voltage signal Vs isadjusted so that voltage and frequency of the signal Vs correspond toset values respectively, namely, a feedback control is carried out forthe output voltage. The sine wave reference signal Vsin is also used forcalculation of an effective power as will be described later.

[0041] The PWM circuit 65 includes a peak limiter circuit 67 as shown inFIG. 5. The peak limiter circuit 67 comprises an operational amplifier68 and an integration circuit 69. The output current signal Is deliveredby the output current detecting circuit 64 is supplied to theoperational amplifier 68. A peak current reference signal Ik is alsosupplied to the operational amplifier 68. When the output current signalIs corresponds to an overcurrent, the operational amplifier 68 is turnedon with respect to a portion where the peak current reference signal Ikis exceeded. The aforesaid peak current reference signal Ik includessignal levels of +Ik and −Ik due to hysteresis as shown in FIG. 6A.Since the integration circuit 69 applies feedback to the operationalamplifier 68, a peak portion of the PWM control signal Vsin′ is cut offsubstantially into a flat portion as shown in FIG. 6C. Without theintegration circuit 69, the PWM control signal Vsin′ delivered by thepeak limiter circuit 69 would instantaneously rise up and fall down suchthat the circuit would oscillate. In the embodiment, however, such aproblem can be solved since the PWM control signal Vsin′ takes asinusoidal waveform when no overcurrent occurs, as shown by broken linein FIG. 6C.

[0042] The PWM circuit 65 includes a comparator 70 comparing theaforesaid PWM control signal Vsin′ with a carrier wave frequency signalSc such as a triangular wave of 16 kHz, for example, as shown in FIG.7A. The carrier wave frequency signal Sc is shown as having anexcessively low frequency for the purpose of illustration in thedrawing. Consequently, the PWM circuit 65 generates drive signals G1 toG4 so that a triangular wave high-frequency voltage V0 (100 V, 50 or 60Hz) as shown in FIG. 7B is obtained. The filter circuit 38 eliminateshigh frequency components from the voltage VO such that AC output V0 acof 100 V, 50 or 60 Hz is produced as shown in FIG. 7C. The PWM controlsignal Vsin′ as shown in FIG. 7A denotes the condition where noovercurrent has occurred.

[0043] The microcomputer 61 serves as a power detector, a phase angledetector, a phase detector and a controller. Upon start of operation,the microcomputer 61 controls an output frequency according to theflowchart of FIG. 8. More specifically, at step Q1, the microcomputer 61detects an initial zero cross in one cycle of the sine-wave referencevoltage Vsin (see timing t0 in FIG. 4). Since an effective zero cross ofthe sine-wave reference signal Vsin corresponds with an effective zerocross of the output voltage V0, timing t0 of the initial zero cross inone cycle of the reference signal Vsin is detected. At step Q2, themicrocomputer 61 determines which an instantaneous value Is(1) of thecurrent is, positive or negative, namely, whether the current leads orlags behind the voltage, thereby detecting whether a phase angle θ is inthe leading or lag phase.

[0044] Thereafter, the instantaneous value Is(n) where n changes from 1to 6 is detected from the output current signal Is six times in a halfcycle at equal time intervals at step Q3. An effective instantaneouspower P(n) is calculated at step Q4. More specifically, themicrocomputer 61 obtains products of the instantaneous values Is(n) attimes (1) to (6) in FIG. 4 and the sine-wave reference signal Vsin(n)which is previously found, storing data of the obtained values. Themicrocomputer 61 further obtains a square of the instantaneous valueI(n) at step Q5, storing data of the obtained value (step Q5). Whensteps Q3 to Q5 have been repeated six times (YES at step Q6), themicrocomputer 61 advances to step Q7 to calculate an effective power P,which is obtained by the equation:

P=P(1)+P(2)+ . . . +P(6).

[0045] The microcomputer 61 advances to step Q8 to calculate aneffective current value I, which is obtained by the equation:

I=((Is(1)²+(Is(2)²+ . . . +(Is(6)²)/6)^(½).

[0046] At step Q9, the microcomputer 61 calculates a phase angle θ. Therelationship between an apparent power (I×E) and the effective power Pis shown by the equation:

P=(I×E)cos θ.

[0047] Accordingly, the phase angle θ is obtained from cos θ since:

Cos θ=P/(I×E).

[0048] When the instantaneous value Is(n) is positive at step Q2, themicrocomputer 61 determines that the phase angle θ is in the leadingphase. On the other hand, when the instantaneous value Is(n) is negativeat step Q2, the microcomputer 61 determines that the phase angle θ is inthe lag phase.

[0049] At step Q10, an output frequency is set on the basis of the phaseangle θ and the leading or lag phase. This setting is executed on thebasis of a data table as shown in FIG. 9. More specifically, when thephase angle is in the leading phase, the output frequency is set so asto become small according to the phase angle θ. The output frequency isset so as to become large according to the phase angle θ when the phaseangle is in the lag phase. For example, the output frequency is 50.0 Hzwhen the phase angle θ is 0°. The output frequency is 50.1 Hz when thephase angle θ is 90°. The output frequency is linearly set between thesevalues.

[0050] The microcomputer 61 has a function of detecting the DC voltageVdc to adjust the output voltage irrespective of an on-off control ofthe thyristors 39 to 41. More specifically, as shown in steps R1 to R3of FIG. 10, when the DC voltage Vdc is at or above 180 V, the outputvoltage is controlled to be increased. That is, the amplitude of thesine wave reference signal Vsin is increased so that the output voltageis increased. For example, when the DC voltage Vdc rises 1 V from 180 V,the output frequency is increased 0.01 Hz.

[0051] Parallel connection of the portable AC power supply units 21 willnow be described. Referring to FIG. 11, two portable AC power supplyunits 21A and 21B are shown. Assume now that the output frequency of theunit 21B has instantaneously reduced to 49.96 Hz for some reason (loadvariation, for example). In this case, a cross current flows from theunit 21A to the unit 21B. In the unit 21B, the current leads the voltageand the phase angle is in the leading phase, whereas the current lagsbehind the voltage in the unit 21A such that the phase angle is in thelag phase. In the embodiment, the output frequency is increased when thephase angle is in the lag phase, and the output frequency is reducedwhen the phase angle is in the leading phase. Accordingly, the outputfrequency is increased in the unit 21A, whereas the output frequency isreduced in the unit 21B. Consequently, an amount of cross currentflowing into the unit to the unit 21A. The output voltage adjustingfunction of the unit 21A detects the DC voltage Vdc which is at or above180 V, thereby increasing the output voltage. As a result, the crosscurrent can be prevented from flowing into the unit 21A.

[0052]FIGS. 13 and 14 show a second embodiment of the invention. Thesecond embodiment differs from the first embodiment in that a wattlesspower is calculated from the effective power so that the outputfrequency is set according to the leading or lag phase of the phaseangle in the wattless power. Steps S1 to S8 in the flowchart of FIG. 13are identical with the steps Q1 to Q8 in FIG. 8 respectively. The valueof cos θ is obtained at step S9. At step S10, the value of sin θ isobtained from cos θ and the wattless power is calculated (wattless powercalculator). The leading or lag phase of the phase angle is determinedat step S2 (phase detector). The phase angle is in the leading phasewhen the instantaneous value I(1) of the current is positive. The phaseangle is in the lag phase when the instantaneous value is negative. Atstep S11, the frequency is set on the basis of the magnitude of thewattless power and the phase with reference to the data table as shownin FIG. 14. For example, when the wattless power in the leading phase isat −2800 W (corresponding to phase angle θ of −90°), the frequency isset at 49.9 Hz. Consequently, the same effect can be achieved from thesecond embodiment as from the first embodiment.

[0053]FIGS. 15A to 15C illustrate a third embodiment of the invention.As another manner of detecting the wattless power, the microcomputer 61sets a signal Vx having a waveform leading the sine wave referencesignal Vsin by 90°. The product of the 21A is reduced such that thecross current is resolved between the units 21A and 21B. In particular,since the output frequency is increased or reduced according to thephase angle θ, the output frequency can be controlled promptly so as totake an optimum value.

[0054] In the foregoing embodiment, the effective power P contains theelement of phase angle θ between the output voltage and the outputcurrent. The effective power P is detected, and the phase angle θ iscalculated on the basis of the detected effective power P. Accordingly,an accurate phase angle θ can be detected even when the output currentor the signal Is detected by the output current detecting circuit 64 haswaveform distortion. Consequently, the accuracy in the detection of thephase angle θ can be improved. Thus, in the frequency control of theoutput voltage, an appropriate frequency control can be performed on thebasis of a phase angle with higher detection accuracy, and the outputcurrents are normally balanced between the power supply units in thecase of the parallel operation.

[0055] Particularly, the effective power is detected in the half cycleof the sine wave reference signal Vsin. Accordingly, the detection ofthe effective power can be executed in a short period of time and thesubsequent frequency control can be carried out quickly. However, theeffective power may be detected in one cycle of the sine wave referencesignal Vsin, instead.

[0056]FIG. 12 illustrates a case where the output voltage of the unit21B is higher than the output voltage of the unit 21A although theoutput frequencies of both units 21A and 21B are the same (50 or 60 Hz).In this case, a cross current flows from the 21B signal Vx and theoutput current signal Is is obtained six times in a half cycle. The sixproducts are added together, whereby the wattless power is detected.Thus, the wattless power can directly be obtained.

[0057]FIGS. 16A to 16D illustrate a fourth embodiment of the invention.The portable AC power supply units 21 of the first and secondembodiments can cope with a case where a relatively small cross currentflows into one of the units in parallel operation. When the crosscurrent is small, the phase angle is not more than 90° and the effectivepower is positive though the phase angle is in the leading or lag phase,as shown in FIG. 16A. However, when the cross current is large,switching elements of the inverter circuit of the unit into which thecross current flow may be damaged. Accordingly, the cross current needsto be resolved or eliminated earlier. In this case, the current signalIs is 90° or more out of phase with the sine wave reference signal Vsin(180° out of phase) and the effective power is negative.

[0058] In view of the above-described problem, an output voltagecontroller is provided for increasing the output voltage when thedetected effective power is negative. Consequently, since a large crosscurrent is prevented from flowing into the power supply unit withoutdetection of the phase angle, phase lead or lag, the switching elementsof the inverter circuit or the like can effectively be prevented frombeing damaged. In this case, an auxiliary controller may be provided forincreasing the frequency of the output voltage when the detectedeffective power is negative. As a result, since the increase in thefrequency reduces an amount of the cross current flowing into the powersupply unit, the same effect can be achieved from the fourth embodimentas from the first embodiment.

[0059] FIGS. 17 to 21 illustrate a fifth embodiment of the invention. Inthe fifth embodiment, the CPU (not shown) of the microcomputer 61 in thefirst embodiment further severs as a corrected value calculator, a phaseangle detector and a sine wave reference data corrector, so that thesine wave reference signal is corrected to prevent variations in theoutput voltage.

[0060] Correction of the sine wave reference signal will now bedescribed with reference to FIG. 17. The correction is executed inparallel with the control as shown in FIG. 8. Upon start of theoperation, the microcomputer 61 delivers the sine wave ref erence signalVsin as will be described later. The PWM circuit 65 delivers a PWMsignal on the basis of the sine wave reference signal Vsin. The invertercircuit 37 controls the switching elements 45 to 48 on the basis of thePWM signal thereby to deliver a high-frequency voltage V₀ as shown inFIG. 7. At this time, the output voltage detecting circuit 63 detectsoutput voltage, and the microcomputer 61 determines whether the outputcurrent signal Is is in the leading or lag phase at zero cross t₀ andzero cross t₁ of the output voltage Vs, as shown in FIG. 20. Morespecifically, when detecting the zero cross t₀ (from the negative to thepositive) of the output voltage signal Vs at step S1 in FIG. 21 anddetecting a positive digital value Id of the output current signal Is atstep S2, the microcomputer 61 determines that the output current signalis in the leading phase. On the other hand, when the digital value Id ofthe output current signal Is is negative, the microcomputer 61determines that the output current signal Is is in the lag phase. Whendetecting the zero cross t₁ (from the positive to the negative) of theoutput voltage signal Vs at step S3 and detecting a negative digitalvalue Id of the output current signal Is at step S4, the microcomputer61 determines that the output current signal Is is in the leading phase.When the digital value Id is positive, the microcomputer 61 determinesthat the output current signal Is is in the lag phase. FIG. 20 shows acase where the detected current Is lags behind the detected voltage Vs.

[0061] At this time, the microcomputer 61 corrects the sine wavereference data D(n) according to the flowcharts of FIGS. 17 and 18thereby to correct the sine wave reference signal Vsin. Morespecifically, the microcomputer 61 sets the parameter n of the sine wavereference data D(n) at 0 at step Q1 in FIG. 17. The microcomputer 61then increments the parameter n at step Q2 and carries out thecorrecting control at step Q3. The correcting control is shown as asubroutine in FIG. 18. At step R1, the microcomputer 61 reads from ROM61 b the sine wave reference data D(n) corresponding to the currentoutput timing. In this case, data D(1) and sine wave reference dataleading the data D(1) by 90° and displaced by a phase angle θ. Forexample, since 256 parameters n are present in 360° of electrical angle(one cycle at 50 or 60 Hz), n is increased to “2,” “3,” “4” and so onfor every increase of (360/256)° when n is “1” at the phase angle of 0°.When converted to time, the aforesaid (360/256)° becomes ({fraction(1/50)} sec.)/256 at 50 Hz and ({fraction (1/60)} sec.)/256 at 60 Hz.

[0062] For example, when the phase angle θ is 30° and in the leadingphase, the parameter n (n=na) becomes sequence “x” which leads na by 90°as shown in FIG. 19. Sequence “y” leads sequence “x” by the phase angleθ. When sequence “y” is out of the range between 1 and 256, the datadisplaced from sequence “y” by 180° is inverted. See “y′” in FIG. 19.The sine wave reference data D(n+90°+θ) is the sine wave reference dataD(y) in this sequence “y”. At step R2, the microcomputer 61 thenmultiplies the data D(n+90°+θ) by a correction value Ih to originatecorrection data Dh. The correction value Ih will be described later. Themicrocomputer 61 then advances to step R3 where the correction data Dhis added to the current sine wave reference data D(n) to obtain new sinewave reference data D(n). Data stored on RAM 61 c is renewed such thatthe new data D(n) is stored on RAM 61 c. The microcomputer 61 furtheradvances to step Q4 in FIG. 17 to deliver the new data D(n) to the D/Aconverter 61 d. An output cycle is set to be at time intervals of 256for {fraction (1/50)} sec. in the frequency of 50 Hz and at timeintervals of 256 for {fraction (1/60)} sec. in the frequency of 60 Hz.

[0063] At step Q7, the microcomputer 61 squares the detected currentvalue Id(n), storing data of the squared value. The microcomputer 61then advances to step Q8 to determine whether n is 128 or 256. Since nis less than 128 at the beginning, the microcomputer 61 determines inthe negative (NO) at step Q8, returning to step Q2. Thus, when steps Q2to Q7 are repeatedly carried out at 128 times or a half cycle iscompleted, the microcomputer 61 determines in the affirmative at stepQ8, advancing to step Q9 where the microcomputer 61 determines whether nis 128. When n is 128, the microcomputer 61 advances to step Q10 tocalculate effective power P when n is 1 to 128. In this case, effectivepower P is obtained by the equation:

P=P(1)+P(2)+ . . . +P(128).

[0064] The microcomputer 61 calculates an effective current value I atstep Q11. The effective current value I is obtained by the equation:

I=((Id(1)² + . . . Id(128)²)/128)^(½).

[0065] Then, the microcomputer 61 obtains the phase angle θ at step Q12.More specifically, the relationship between an apparent power (I×E) andthe effective power P is shown by the equation:

P=(I×E)cos θ.

[0066] Accordingly, the phase angle θ is obtained from cos θ since:

Cos θ=P/(I×E).

[0067] In an initial half cycle, the result of detection at step S2 inFIG. 21 is the latest. The phase angle θ is in the leading phase whenthe latest result of detection is positive. On the other hand, the phaseangle θ is in the lagging phase when the result of detection isnegative.

[0068] A correction value Ih is calculated at step Q13. The correctionvalue is obtained by multiplying a factor k by an effective value I ofcurrent. The factor k depends upon the reactor 55 of the filter circuit38 etc. Thereafter, the microcomputer 61 returns to step Q2 to carry outthe same control in a latter half cycle (where n=129 to 256) asdescribed above for the first half cycle. The phase angle θ and thecorrection value Ih obtained in the first half cycle (where n=1 to 128)are used in the latter half cycle. When the control at steps Q2 throughQ7 is executed at 256 times, the microcomputer 61 determines in theaffirmative at step Q8 and in the negative at step Q9, executing stepsQ14 to Q17 which are substantially identical with respective steps Q10to Q13 with the exception of n=129 to 256. The microcomputer 61 thenreturns to step Q1. Thus, the sine wave reference data D(n) for onecycle is supplied to the D/A converter 61 d. The D/A converter 61 ddelivers the sine wave reference signal Vsin on the basis of thesupplied data D(n). The delivered sine wave reference signal Vsin issupplied to the PWM circuit 65.

[0069] According to the above-described embodiment, the microcomputer 61reads out the sine wave reference data D(n) corresponding to the currentoutput timing. The microcomputer 61 further reads out the sine wavereference data D(y) leading the read data D(n) by 90° and shifted by thephase angle θ relative to the read data D(n). The microcomputer 61multiplies the correction value Ih by the read sine wave reference dataD(y) to obtain correction data Dh. The microcomputer 61 further adds thecorrection data Dh to the sine wave reference data D(n) corresponding tothe current output timing to obtain new sine wave reference data D(n).Thus, data correction is performed in consideration of the lag of 90°due to the filter circuit 38, the phase angle θ of the output currentdue to the load and an L component peculiar to the filter circuit 38.The corrected sine wave reference data D(n) is delivered to the D/Aconverter 61 d, which delivers the sine wave reference signal correctedon the basis of the corrected sine wave reference data D(n).Consequently, the variations in the output voltage can be reduced.Further, the above-described arrangement requires no analog circuit suchas a differential amplifier including resistors and capacitors or apower factor correcting circuit including resistors, capacitors and anoperational amplifier. Consequently, the circuit arrangement can besimplified and accordingly, the cost can be reduced.

[0070] The current value Id is detected in the half cycle of the outputvoltage signal Vs corresponding to the half cycle of the output voltage,and the effective current value I is calculated. Consequently, theoutput current value can be detected in a short period of time, and thedetected effective value I contains a reduced amount of error detection.On the other hand, the current value Id may be detected in one cycle ofthe output voltage signal Vs, instead. Further, the effective power P iscalculated on the basis of the sine wave reference data D(n) in the halfcycle and the effective value I, and the phase angle θ is calculated onthe basis of the effective power P in the half cycle. Consequently, thephase angle can be detected in a short period of time. On the otherhand, the effective power P may be calculated on the basis of the dataD(n) detected in one cycle.

[0071] Further, each of calculation of the correction value Ih anddetection of the phase angle θ may be carried out in a half cycle of theoutput voltage signal Vs. The obtained correction value Ih and phaseangle θ are used for correction of the data D(n) and output of thesignal Vsin in the next half cycle. Consequently, the control forcorrection of the sine wave reference signal Vsin can be performedquickly such that a quick feedback control can be realized.

[0072] The sine wave reference data D(n) corresponding to 256 phaseangles in one cycle of the AC voltage to be delivered are stored in theforegoing embodiments. The number of data should not be limited to 256.Further, the data in a half cycle of the AC voltage may be stored,instead. In this case, since the polarity in a first half cycle isinverted in the next half cycle, the data used in the first half cycleneeds to be inverted in the next half cycle.

[0073] The foregoing description and drawings are merely illustrative ofthe principles of the present invention and are not to be construed in alimiting sense. Various changes and modifications will become apparentto those of ordinary skill in the art. All such changes andmodifications are seen to fall within the scope of the invention asdefined by the appended claims.

We claim:
 1. An inverter comprising: a DC power supply circuit; aninverter circuit having a plurality of switching elements and switchingan output of the DC power supply circuit on the basis of a PWM signal todeliver a high-frequency voltage; a filter circuit converting thehigh-frequency voltage to a substantially sinusoidal AC voltage; a powerdetector detecting an effective or wattless power of the AC power; aphase angle calculator calculating a phase angle of current relative tovoltage from the detected effective or wattless power; a phase detectordetecting a leading or lagging state of the phase angle; and acontroller decreasing a frequency of the output voltage when the phasedetector detects the leading state of the phase angle, the controllerincreasing the frequency of the output voltage when the phase detectordetects the lagging state of the phase angle.
 2. An inverter accordingto claim 1, wherein the power detector detects the effective power ofthe AC output, the phase angle calculator calculates the phase angle ofthe current relative to the voltage from the effective power detected bythe power detector, and the controller decreases the frequency of theoutput voltage according to the phase angle when the phase detectordetects the leading state of the phase angle.
 3. An inverter accordingto claim 1, wherein the power detector detects the effective power ofthe AC output, which further comprises a wattless power calculatorcalculating a wattless power on the basis of the effective powerdetected by the power detector, and wherein the controller decreases thefrequency of the output voltage according to the wattless power when thephase detector detects the leading state of the phase angle, thecontroller increasing the frequency of the output voltage according tothe wattless power when the phase detector detects the lagging state ofthe phase angle.
 4. An inverter according to claim 2, wherein the powerdetector detects the effective power at least in a half cycle of a sinewave reference signal.
 5. An inverter according to claim 1, wherein thePWM signal is produced on the basis of a sine wave reference signal, thepower detector detects the wattless power on the basis of a detectedvalue of an output current and a signal leading the sine wave referencesignal by an electrical angle of 90 degrees, and the controllerdecreases the frequency of the output voltage according to the wattlesspower when the phase detector detects the leading state of the phaseangle, the controller increasing the frequency of the output voltageaccording to the wattless power when the phase detector detects thelagging state of the phase angle.
 6. An inverter according to claim 2,further comprising an output voltage controller increasing the outputvoltage when the detected effective power is negative.
 7. An inverteraccording to claim 2, further comprising an auxiliary controllerincreasing the frequency of the output voltage when the detectedeffective power is negative.
 8. An inverter according to claim 1,further comprising: a storage device storing a number of sine wavereference data corresponding to a number of phase angles at least in ahalf cycle of an alternating current respectively; a sine wave referencesignal generator to which the sine wave reference data are sequentiallysupplied to generate a sine wave reference signal with a predeterminedfrequency; a PWM circuit generating the PWM signal on the basis of thesine wave reference signal to operate the inverter circuit; an outputcurrent detector detecting a value of current produced by the invertercircuit; a corrected value calculator calculating a corrected value onthe basis of the current value detected by the output current detector;and a sine wave reference data corrector reading from the storage devicethe first sine wave reference data corresponding to a current outputtiming and the second sine wave reference data leading the first sinewave reference data by 90 degrees and displaced from the first sine wavereference data by a phase angle, the sine wave reference data correctormultiplying the read second sine wave reference data by the correctedvalue to produce corrected data, the sine wave reference data correctoradding the corrected data to the first sine wave reference datacorresponding to the current output timing to produce new sine wavereference data, the sine wave reference data corrector causing the newsine wave reference data to be stored on the storage device so that datathereon is renewed, and delivering the new sine wave reference data tothe sine wave reference signal generator.
 9. An inverter according toclaim 8, wherein the output current detector detects the current valueat least in a half cycle of the output voltage to calculate theeffective value.
 10. An inverter according to claim 8, wherein the phaseangle calculator calculates the effective power from sine wave referencedata at least in a half cycle and the value detected by the outputcurrent detector to calculate the phase angle from the calculatedeffective power.
 11. An inverter according to claim 8, wherein thecorrected value calculator calculates the corrected value at least in ahalf cycle of the output voltage, the phase angle calculator calculatesthe phase angle at least in the half cycle of the output voltage, andthe sine wave reference data corrector carries out control in asubsequent half cycle of the output voltage using the calculatedcorrected value and phase angle.